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    • 专利摘要:
    The invention relates to an AC / DC converter comprising: an H (H1) bridge; an inductance (LI) in series with an input of the bridge; an inductance (LO) in series with an output of the bridge; and a circuit (501) adapted to control the bridge alternately in a first configuration in which first (S1, S3) and second (S2, S4) diagonals of the bridge are respectively conducting and blocked, and in a second complementary configuration, the circuit (501) being adapted, during a transition phase between the first and second configurations, to: close a first switch (S2) of the second diagonal; opening a first switch (S1) of the first diagonal when the current flowing through this switch is canceled; close the second switch (S4) of the second diagonal; and open the second switch (S3) of the first diagonal when the current flowing through this switch is canceled.
    公开号:FR3061817A1
    申请号:FR1750209
    申请日:2017-01-10
    公开日:2018-07-13
    发明作者:Leo Sterna；Othman LADHARI；Jean-Paul Ferrieux；David Frey；Pierre-Olivier Jeannin
    申请人:Commissariat a lEnergie Atomique CEA；Commissariat a lEnergie Atomique et aux Energies Alternatives CEA；
    IPC主号:
    专利说明:

    © Holder (s): COMMISSION OF ATOMIC ENERGY AND ALTERNATIVE ENERGIES Public establishment.
    © Agent (s): CABINET BEAUMONT.
    FR 3 061 817 - A1 © AC-DC POWER CONVERTER.
    The invention relates to an AC / DC converter, comprising:
    an H-bridge (H1);
    an inductor (L1) in series with a bridge input; an inductor (LO) in series with an output of the bridge; and a circuit (501) adapted to control the bridge alternately in a first configuration in which first (S1, S3) and second (S2, S4) diagonals of the bridge are respectively passing and blocked, and in a second complementary configuration, the circuit (501) being adapted, during a transition phase between the first and second configurations, to:
    close a first switch (S2) on the second diagonal;
    open a first switch (S1) of the first diagonal when the current passing through this switch is canceled;
    close the second switch (S4) on the second diagonal; and open the second switch (S3) of the first diagonal when the current passing through this switch is canceled.
    500

    B15711 - DD17721SP
    AC-DC POWER CONVERTER
    Field
    The present application relates to the field of power converters, and relates more particularly to an AC-DC converter, that is to say a converter adapted to convert an alternating voltage into a direct voltage. Presentation of the prior art
    An AC-DC converter conventionally comprises a rectification stage of the alternating voltage applied to its input, comprising one or more diodes, followed by a low-pass filtering stage of the rectified alternating voltage delivered by the rectification stage, followed by a DC-DC conversion stage (continuous) of the direct voltage delivered by the low-pass filtering stage, typically a switching conversion stage comprising one or more controlled switches and an isolation transformer.
    A drawback of converters of this type lies in their relatively large cost and size, resulting from the large number of components which they comprise and the size of these components.
    In particular, the low-pass filtering stage conventionally comprises a large capacitor, typically a capacitor of several tens of microfarads and several
    B15711 - DD17721SP hundreds of volts for a converter intended to receive on its AC input an AC voltage of 220 V, for example the mains voltage.
    In addition, to limit switching losses in the switching DC-DC conversion stage, the operating frequency of the conversion stage (or switching frequency) is generally limited to a few hundred kHz, which restricts the possibilities of miniaturization of the DC-DC conversion stage, and in particular of the isolation transformer.
    Another drawback of converters of this type is that the presence of the diode rectification stage significantly limits the efficiency of the converter.
    Furthermore, in certain applications in which the converter is used to supply an active DC load, for example a battery, there is a need for a reversible converter, that is to say able not only to convert the input voltage alternative to a DC output voltage to supply the load (typically to charge a battery from an AC voltage), but also to convert a DC voltage supplied by the load into an AC voltage supplied on the AC input terminals of the converter (typically for re-injecting electrical energy drawn from the battery into the alternative network). Due to their architecture, and in particular due to the presence of the diode rectification stage and the low-pass filtering stage, the converters of the type described above do not make it possible to ensure such reversibility.
    US Pat. No. 6,424,548 describes an AC-DC converter with so-called direct conversion switching, that is to say not comprising a diode rectification stage nor a low-pass filtering stage upstream of the switching conversion stage. . More particularly, this converter comprises four bidirectional switches forming a first controlled H-bridge, followed by an isolation transformer comprising a primary winding and
    B15711 - DD17721SP a secondary winding magnetically coupled, followed by four quasi-bidirectional switches forming a second H-controlled bridge. The input of the first H-bridge directly receives the AC voltage to be converted, the primary winding of the transformer is connected between the output terminals of the first H-bridge, the secondary winding of the transformer is connected between the input terminals of the second H-bridge, and the DC load to be supplied is connected between the output terminals of the second H-bridge.
    An advantage of this converter is that it does not have a diode rectification stage nor a low pass filtering stage upstream of the switching conversion stage, which makes it possible to reduce the cost and the bulk and improve performance compared to traditional solutions. In addition, this converter is reversible.
    However, as in traditional converters, the switching losses in the switching conversion stage prevent in practice increasing the switching frequency of the switches beyond a few hundred kHz, which limits the possibilities of miniaturization of the system. , and in particular the isolation transformer.
    It would be desirable to have an AC-DC converter which overcomes all or part of the aforementioned drawbacks of existing converters.
    summary
    Thus, one embodiment provides a circuit for converting an alternating voltage into a direct voltage, comprising:
    four first bidirectional switches forming a first H-shaped bridge, first and second bridge input nodes being connected respectively to first and second nodes for applying AC voltage;
    a transformer comprising a primary winding and a secondary winding magnetically coupled, first and second ends of the primary winding being connected
    B15711 - DD17721SP respectively to first and second output nodes of the first bridge;
    a first inductor connected in series with the first bridge between the first input node of the bridge and the first node for applying the AC voltage;
    a second inductor connected in series with the first bridge, between the first output node of the bridge and the first end of the primary winding; and a control circuit adapted to control the first bridge alternately in a first configuration in which the switches of a first diagonal of the bridge are closed and the switches of a second diagonal of the bridge are open, and in a second configuration in which the switches of the first diagonal are open and the switches of the second diagonal are closed, the control circuit being adapted, during a transition phase between the first and second configurations, to, successively:
    close a first switch on the second diagonal r open a first switch on the first diagonal when the current flowing through this switch is canceled;
    close the second switch of the second diagonal; and open the second switch of the first diagonal when the current passing through this switch is canceled.
    According to one embodiment, the conversion circuit further comprises four second switches forming a second H-bridge, first and second input nodes of the second bridge being connected respectively to first and second ends of the secondary winding of the transformer , and first and second output nodes of the second bridge being connected respectively to first and second nodes for supplying the DC voltage.
    B15711 - DD17721SP
    According to one embodiment, the control circuit is adapted to control the second bridge alternately in a first configuration in which the switches of a first diagonal of the bridge are closed and the switches of a second diagonal of the bridge are open, and in a second configuration in which the switches of the first diagonal are open and the switches of the second diagonal are closed.
    According to one embodiment, the control circuit is configured to switch the first bridge between its first and second configurations and to switch the second bridge between its first and second configurations at substantially the same frequency.
    According to one embodiment, the control circuit is configured to switch the first bridge between its first and second configurations at a frequency greater than or equal to 1 MHz.
    According to one embodiment, each first switch is adapted to be commanded to close by the control circuit and to open automatically when the current flowing through it is canceled.
    According to one embodiment, each first switch is equivalent to an anti-series association of first and second MOS transistors connected by their drains, the sources of the first and second transistors respectively forming the conduction nodes of the switch, and the gates first and second MOS transistors forming first and second switch control nodes.
    According to one embodiment, the control circuit is configured to, when it commands the closing of a switch of the first bridge, apply a closing control signal to the gate of one of the first and second transistors of 1 ' switch and maintain a blocking signal on the gate of the other transistor.
    B15711 - DD17721SP
    According to one embodiment, the control circuit is configured to, when it controls the closing of a switch of the first bridge, apply a closing control signal to the gate of the first transistor and a blocking signal on the gate of the second transistor when the current which the switch must conduct is of a first polarity, and apply a closing control signal to the gate of the second transistor and a blocking signal to the gate of the first transistor when the current which is to conduct l the switch has a second polarity opposite to the first polarity.
    According to one embodiment, the first switches are switches with gallium nitride.
    Another embodiment provides a circuit for converting an alternating voltage into a direct voltage, comprising:
    four first bidirectional switches forming a first H-bridge, first and second bridge input nodes being directly connected respectively to first and second nodes for applying AC voltage;
    a first capacitor connected in parallel with the first bridge between the first and second input nodes of the bridge;
    a second capacitor connected in parallel with the first bridge between first and second bridge output nodes; and a control circuit adapted to control the bridge alternately in a first configuration in which the switches of a first diagonal of the bridge are closed and the switches of a second diagonal of the bridge are open, and in a second configuration in which the switches of the first diagonal are open and the switches of the second diagonal are closed, the control circuit being adapted, during a transition phase between the first and second configurations, to, successively:
    open the switches of the first diagonal; and
    B15711 - DD17721SP for each switch of the second diagonal, close the switch only when the voltage across its terminals is zero.
    According to one embodiment, the conversion circuit further comprises four additional capacitors connected respectively to the terminals of the first four switches.
    According to one embodiment, the conversion circuit further comprises a transformer comprising a primary winding and a secondary winding magnetically coupled, first and second ends of the primary winding being connected respectively to first and second output nodes of the first bridge. .
    According to one embodiment, the conversion circuit further comprises four second switches forming a second H-bridge, first and second input nodes of the second bridge being connected respectively to first and second ends of the secondary winding of the transformer , and first and second output nodes of the second bridge being connected respectively to first and second nodes for supplying the DC voltage.
    According to one embodiment, the control circuit is adapted to control the second bridge alternately in a first configuration in which the switches of a first diagonal of the bridge are closed and the switches of a second diagonal of the bridge are open, and in a second configuration in which the switches of the first diagonal are open and the switches of the second diagonal are closed.
    According to one embodiment, the control circuit is configured to switch the first bridge between its first and second configurations and to switch the second bridge between its first and second configurations at substantially the same frequency.
    According to one embodiment, the control circuit is configured to switch the first bridge between its first and
    B15711 - DD17721SP second configurations at a frequency greater than or equal to 1 MHz.
    According to one embodiment, the control circuit comprises, for each first switch:
    a first circuit adapted to detect a cancellation of the voltage at the terminals of the switch and to supply a logic output signal corresponding to the result of this detection;
    a second circuit adapted to perform a logic operation between the signal supplied by the first circuit and an external switch control signal, and to supply a logic control signal for the switch corresponding to the result of this operation; and a third circuit adapted to carry out a level adaptation of the signal supplied by the second circuit to control the switch accordingly.
    According to one embodiment, each first switch is equivalent to an anti-series association of first and second MOS transistors connected by their sources, the drains of the first and second transistors respectively forming the conduction nodes of the switch, and the gates first and second MOS transistors being connected to the same switch control node.
    According to one embodiment, the first circuit comprises a voltage comparator, a first voltage divider bridge connected between the drain and source nodes of the first transistor and of which an output node is connected to a positive input node of the comparator , and a second voltage divider bridge connected between the drain and source nodes of the second transistor and of which an output node is connected to a negative input node of the comparator.
    According to one embodiment, the first switches are switches with gallium nitride.
    Brief description of the drawings
    These and other features and advantages will be discussed in detail in the following description of modes of
    B15711 - DD17721SP particular realization made without limitation in relation to the attached figures among which:
    Figure 1 is an electrical diagram of an example of an AC-DC converter according to a first embodiment;
    Figure 2 is a timing diagram illustrating the operation of the converter of Figure 1;
    Figure 3 is a block diagram illustrating an exemplary embodiment of a control circuit of a switch of the converter of Figure 1;
    Figure 4 is a more detailed diagram of an exemplary embodiment of a switch of the converter of Figure 1 and the control circuit of this switch;
    FIG. 5 is an electrical diagram of an example of an AC-DC converter according to a second embodiment;
    Figure 6 is a timing diagram illustrating the operation of the converter of Figure 5; and FIGS. 7A and 7B illustrate an exemplary embodiment of a switch of the converter of FIG. 5. Detailed description
    The same elements have been designated by the same references in the different figures and, moreover, the various figures are not drawn to scale. For the sake of clarity, only the elements useful for understanding the described embodiments have been shown and are detailed. In particular, the applications which can be made of the AC-DC converters described have not been detailed, the embodiments described being compatible with the usual applications of AC-DC converters. In addition, the control circuits of the switches of the converters described are only partially detailed, the complete production of these control circuits being within the reach of those skilled in the art from the indications of this description. Unless specified otherwise, the expressions approximately, appreciably, and of the order of mean to the nearest 10%, preferably to the nearest 5%. In addition, we use the term connected to designate a connection
    B15711 - DD17721SP direct electrical, without intermediate electronic component, for example by means of one or more conductive tracks or conductive wires, and the term coupled or the term connected, to designate an electrical connection which can be direct (meaning then connected) or indirect (i.e. via one or more intermediate components).
    First embodiment - capacitive structure
    FIG. 1 is an electrical diagram of an example of an AC-DC converter 100 according to a first embodiment.
    The converter 100 comprises a first H-controlled bridge H1, or primary bridge, followed by an isolation transformer T, followed by a second H-controlled bridge H2, or secondary bridge.
    The bridge H1 consists of four switches controlled bidirectionally in current and voltage SI, S2, S3 and S4, for example identical (apart from manufacturing dispersions), each comprising two main conduction nodes and at least one control node. The switches SI and S4 are connected in series, by their conduction nodes, between input nodes C and D of the bridge. The switches S2 and S3 are connected in series, by their conduction nodes, between the nodes C and D, in parallel with the branch comprising the switches SI and S4. The midpoint E between the switches SI and S4 defines a first output node of the bridge, and the midpoint F between the switches S2 and S3 defines a second output node of the bridge. More particularly, in the example shown, the switch SI has a first conduction node connected to the node C and a second conduction node connected to the node E, the switch S4 has a first conduction node connected to the node E and a second conduction node connected to node D, the switch S2 has a first conduction node connected to node C and a second conduction node connected to node F,
    B15711 - DD17721SP and switch S3 has a first conduction node connected to node F and a second conduction node connected to node D.
    The input nodes C and D of the bridge H1 are directly connected, that is to say without intermediate diode rectification stage or low-pass filtering, to nodes A and B of application of the alternating voltage d input of the converter. The term “low-pass filtering stage” is understood here to mean a low-pass filtering stage with a cutoff frequency approximately equal to or less than the frequency of the converter input AC voltage. Low-pass filtering elements with a higher cut-off frequency may however be provided, in particular for filtering any spurious signals generated during the switching of the switches of the bridge H1. More particularly, in this example, the node C is connected to the node A via an inductor 11, and the node D is connected to the node B. The function of the inductor 11 is to filter possible voltage peaks interference generated when the switches of the bridge H1 are switched. In the example shown, the inductor 11 has a first end connected to the node A and a second end connected to the node C. Alternatively, the inductor 11 can be omitted, the node C then being connected to the node A.
    According to one aspect of the first embodiment, the primary bridge H1 is purely capacitive at the input and at the output. More particularly, the converter 100 comprises a capacitor CI whose electrodes are connected respectively to the input nodes C and D of the bridge Hl, and a capacitor CO whose electrodes are connected respectively to the output nodes E and F of the bridge Hl. Note that this is an unusual arrangement. Indeed, in power electronics, there are generally provided passive elements for exchanging electrical energy of different natures at the input and output of the same H-bridge, for reasons of compliance with the rules of association of sources.
    In this example, the converter 100 further comprises four capacitors C1, C2, C3, C4, for example identical (aux
    B15711 - DD17721SP near manufacturing dispersions), respectively connected in parallel with switches SI, S2, S3, S4 of bridge H1. More particularly, each capacitor Ci, with i integer ranging from 1 to 4, has its electrodes connected respectively to the conduction nodes of the switch Si of the same index i.
    The transformer T comprises a primary winding W1 and a secondary winding W2 magnetically coupled.
    The ends G and H of the primary winding W1 are connected respectively to the nodes E and F of the output of the bridge H1. More specifically, in the example shown, the end G of the primary winding W1 is connected to the node E via an inductor 12, and the end H of the primary winding W1 is connected to the node F The inductance 12 has the role of filtering possible spurious voltage peaks. In the example shown, the inductor 12 has a first end connected to the node G and a second end connected to the node E. As a variant, the inductor 12 can be omitted, the node G then being connected to the node E.
    The bridge H2 consists of four controlled switches S5, S6, S7 and S8, for example identical (apart from manufacturing dispersions), each comprising two main conduction nodes and at least one control node. The switches S5, S6, S7 and S8 are for example quasi-bidirectional switches, that is to say adapted to allow current to flow in both directions, but only allowing current control in one direction, it that is to say that can only be controlled in the blocked state when a voltage of a determined polarity is applied between their conduction nodes (in other words bidirectional switches in current but unidirectional in voltage). As a variant, the switches S5, S6, S7, S8 are bidirectional current and voltage switches. The switches S5 and S8 are connected in series, by their conduction nodes, between input nodes K and L of the bridge. Switches S6 and S7 are connected in series, by their conduction nodes, between nodes K and L, in parallel with the branch
    B15711 - DD17721SP including switches S5 and S8. The midpoint M between switches S5 and S8 defines a first output node of the bridge, and the midpoint N between switches S6 and S7 defines a second output node of the bridge. More particularly, in the example shown, the switch S5 has a first conduction node connected to the node L and a second conduction node connected to the node M, the switch S8 has a first conduction node connected to the node M and a second conduction node connected to node K, switch S6 has a first conduction node connected to node L and a second conduction node connected to node N, and the switch S7 has a first conduction node connected to node N and a second conduction node connected to node K.
    The input nodes K and L of the bridge H2 are connected respectively to the ends I and J of the secondary winding W2 of the transformer T. In the example shown, the end I of the winding W2 is connected to the node K and the end J of the winding W2 is connected to the node L.
    The converter 100 further comprises an output filtering capacitor CF, at the output of the bridge H2. In the example shown, the electrodes of the capacitor CF are connected respectively to the nodes M and N of the output of the bridge H2.
    The output nodes M and N of the bridge H2 are connected respectively to nodes O and P for supplying the DC output voltage of the converter 100. In the example
    represented, the node M and connected to node 0 and node N is connected to node P. The converter 100 further includes a circuit 101 (not detailed) order of switches if, S2, S3, S4, S5,
    S6, S7 and S8 of bridges H1 and H2.
    In operation, a load L to be supplied, for example an electric battery, can be connected between the nodes O and P of the converter output.
    The operation of the converter 100 is as follows.
    Circuit 101 controls the primary bridge H1 alternately in
    B15711 - DD17721SP a first configuration in which the switches SI and S3, defining a first diagonal of the bridge, are closed (passers-by) and the switches S2 and S4, defining a second diagonal of the bridge, are open (blocked), and in a second configuration in which the switches SI and S3 are open and the switches S2 and S4 are closed. The switching frequency of the bridge H1 between the first and second configurations, called the switching frequency, is preferably chosen to be much higher than the frequency of the AC voltage to be converted, for example between 200 kHz and 20 MHz for an input frequency. on the order of 20 to 100 Hz. The duty cycle φΗΙ of the switching between the first and second configurations of the bridge H1 is for example approximately equal to 0.5.
    The circuit 101 also controls the secondary bridge H2 alternately in a first configuration in which the switches S5 and S7, defining a first diagonal of the bridge, are closed and the switches S6 and S8, defining a second diagonal of the bridge, are open, and in a second configuration in which the switches S5 and S7 are open and the switches S6 and S8 are closed. The switching frequency of the bridge H2 between the first and second configurations is substantially equal to the switching frequency of the bridge H1. During the transition from the first configuration to the second configuration, the circuit 101 can also control the bridge H2 in a first intermediate configuration in which the switches S5 and S8 are closed and the switches S6 and S7 are open. In addition, during the transition from the second configuration to the first configuration, the circuit 101 can control the bridge H2 in a second intermediate configuration in which the switches S5 and S8 are open and the switches S6 and S7 are closed.
    The duty cycle φΗ2 of the switching between the first and second configurations of the bridge H2 can however be different from the duty cycle φΗΙ of the primary bridge. In addition, a
    B15711 - DD17721SP phase shift ÔH1H2 can be provided between the control sequence of the primary bridge H1 and the control sequence of the secondary bridge H2.
    By playing on parameters φΗ2 and ÔH1H2, the circuit
    101 regulates the DC output voltage of the converter 100, and / or the current drawn from the supply voltage source of the converter, alternative absorption.
    by sine of the example current supplied for by
    From the alternative figure ensure a source
    Thus, in battery, is 101 can, in the aforementioned, of the converter charge.
    more, the converter of the case where a load L active, is reversible.
    for example one connected at the converter output, the circuit playing on the parameters φΗΙ, φΗ2 and / or ÔH1H2 controlling a continuous
    According to an aspect of DC-AC electrical energy transfer,
    L to the alternative input when the voltage at their transition terminals between the blocked and diagonal of the embodiment, during the phases (diagonal SI, and the second the of
    S3 and the diagonal S2, S4 switches S2 and cancels, and, during the second configuration (diagonal S2, S4 passing) and the first S3 passing and diagonal S2, S4 of the first control circuit mode 101 is configured for, transition between the first pass and diagonal configuration S2, S4 blocked) configuration (diagonal SI, S3 blocked pass) of the primary bridge Hl, close S4 only in phases SI, S3 configuration (diagonal SI, blocked) of the bridge Hl, close the switches SI and S3 only when the voltage across their terminals is canceled.
    This makes it possible to significantly limit the switching losses in the primary bridge H1. The switching frequency of the converter can then be chosen to be relatively high, for example greater than 1 MHz or even greater than 10 MHz, which makes it possible to significantly reduce the dimensions of the isolation transformer T.
    B15711 - DD17721SP
    In a preferred embodiment, the switches SI, S2, S3, S4 of the primary bridge H1 and the switches S5, S6, S7, S8 of the secondary bridge H2 are gallium nitride switches, for example switches of the type described in patent application EP2736078 previously filed by the applicant, or in the article entitled The single reference Bi-Directional GaN HEMT AC switch by D. Bergogne et al. (Power Electronics and Applications (EPE'15 ECCE-Europe)). Gallium nitride switches are indeed able to operate at high switching frequencies without risk of degradation. However, the embodiments described are not limited to this particular example.
    FIG. 2 is a timing diagram illustrating the operation of the converter 100 of FIG. 1 during a transition phase from the first configuration (diagonal SI, S3 passing and diagonal S2, S4 blocked) to the second configuration (diagonal SI, S3 blocked and diagonal S2, S4 passing) of the primary bridge H1.
    More particularly, the timing diagram of FIG. 2 comprises a first curve Vqq representing the evolution, as a function of time, of the voltage Vqq at the terminals of the output capacitor CO of the primary bridge Hl, a second curve Vgj_ representing the evolution, in as a function of time, of the voltage Vgj_ at the terminals of the switch SI, and a third curve Vgg representing the evolution, as a function of time, of the voltage Vgg at the terminals of the switch S2.
    In the example of FIG. 2, one places oneself at an initial instant t0 at which the primary bridge H1 is in the first configuration. The switches SI and S3 are then conducting and the switches S2 and S4 blocked, and the voltage Vqq at the terminals of the capacitor CO is substantially equal to the value V e of the alternating input voltage of the converter at the instant considered, from l 'order of 200 Volts in the example shown. Taking into account that the converter switching frequency is much higher than the frequency of the alternating voltage
    B15711 - DD17721SP input of the converter, the alternating input voltage is considered constant throughout the duration of a transition phase between the first and second configurations of the H1 bridge. At time t0, the voltage Vgj_ across the switch SI is substantially zero (switch SI on), and the voltage Vgg across the switch S2 is substantially equal to the value V e (switch S2 blocked).
    At an instant tl posterior to the instant tO, marking the beginning of a transition phase between the first and second configurations of the primary bridge Hl, the circuit 101 commands the opening of the switches SI and S3, while maintaining the switches S2 and S4 in the open state. To ensure the continuity of the current flowing in the inductor 12 and / or in the inductor formed by the winding W1 of the transformer T, the capacitor CO then discharges completely, to a zero value, then charges negatively until at the value -V e . During the phase of discharge and then of negative charge of the capacitor CO, the voltage Vgj_ across the terminals of the switch SI increases until reaching the value V e , and the voltage Vgg across the terminals of the switch S2 decreases to a value nothing.
    The control circuit 101 is configured to detect the cancellation of the voltage Vgg at the terminals of the switch S2 according to the instant tl of opening of the switches SI and S3, and to control the closing of the switch S2 when the Vgg voltage cancellation is detected.
    Thus, at an instant t2 posterior to the instant tl, corresponding to the instant of cancellation of the voltage across the terminals of the switch S2, the circuit 101 commands the closing of the switch S2.
    It will be noted that the voltages V33 and V34 at the terminals of the switches S3 and S4 have not been shown in FIG. 2, these voltages having substantially the same evolution as the voltages Vgj_ and Vgg respectively.
    The instant t2 marks the end of the transition phase between the first and second configurations of the primary bridge
    B15711 - DD17721SP
    H1. The switches S2 and S4 are then conducting and the switches SI and S3 blocked, and the voltage Vqq at the terminals of the capacitor CO is substantially equal to the value -V e , of the order of -200 Volts in the example shown. At time t2, the voltage Vgg across the switch S2 is substantially zero, and the voltage Vgj_ across the switch SI is substantially equal to the value V e .
    The operation of the converter 100 during the transition phases from the second configuration (diagonal SI, blocked S3 and diagonal S2, S4 passing) to the first configuration (diagonal SI, S3 passing and diagonal S2, S4 blocked) of the primary bridge H1 is similar to what has just been described, that is to say that the circuit 101 first controls the opening of the switches S2 and S4, while maintaining the switches SI and S3 in the open state, then monitors the voltage at the terminals of switches SI and S3 so as to command the closing of switches SI and S3 only when the voltage at their terminals is canceled.
    FIG. 3 schematically and partially illustrates an exemplary embodiment of the control circuit 101 of the converter 100 of FIG. 1. FIG. 3 more particularly illustrates a switch Si of the primary bridge H1 of the converter, as well as an associated control circuit to this switch. The control circuit shown in Figure 3 corresponds to a part of the control circuit 101 in Figure
    1. By way of example, each of the switches SI, S2, S3, S4 of the primary bridge H1 of the converter, is associated with a specific control circuit of the type described in relation to FIG. 3.
    The control circuit of FIG. 3 comprises, connected to the switch Si by its main conduction nodes, a circuit 301 for detecting the transition to a value zero or considered to be zero of the voltage across the terminals of the switch Si. L 'stage 301 provides a logic output signal indicating whether or not the voltage across the switch Si is considered to be zero.
    B15711 - DD17721SP
    The control circuit of FIG. 3 further comprises a circuit 303 receiving the logic output signal from stage 301, and also receiving an external control signal CMDgxT 'supplied by a centralized control circuit (not detailed) of the circuit 101 of FIG. 1. The circuit 303 performs a logic operation between the output signal of the circuit 301 and the external control signal CMDgxT 'and supplies a logic control signal of the switch Si, corresponding to the result of this operation. By way of example, to switch the bridge H1 from the first configuration (diagonal SI, S3 passing and diagonal S2, S4 blocked) to the second configuration (diagonal SI, S3 blocked and diagonal S2, S4 passing), the centralized circuit for controlling the circuit 101 simultaneously sends an order to open the switch SI, an order to authorize the closing of the switch S2, an order to open the switch S3, and an order to authorize the closing of switch S4, via the inputs of circuits 303 associated with switches
    SI, S2, S3 and S4 respectively. Similarly, to switch the bridge H1 from the first configuration (diagonal SI, blocked S3 and diagonal S2, S4 passing) to the second configuration (diagonal SI, S3 passing and diagonal S2, S4 blocked), the centralized control circuit of the circuit 101 simultaneously sends an authorization order to close the switch SI, an order to open the switch S2, an order to authorize the closing of the switch S3, and an order to open the 'switch S4, via the inputs of circuits 303 associated with switches SI, S2, S3 and S4 respectively.
    For each switch Si, when the circuit 303 associated with the switch receives an order to open the switch, it directly applies a command signal to open on its output, without taking account of the output signal from circuit 301.
    When the logic circuit 303 associated with a switch Si receives an authorization to close the switch,
    B15711 - DD17721SP it starts by maintaining on its output a control signal in the open state of the switch as long as the output signal of circuit 301 does not indicate a cancellation of the voltage across the terminals of the switch, then it applies on its output a command signal to close the switch If only when the output signal from circuit 301 induces a cancellation of the voltage across the switch.
    The control circuit of FIG. 3 further comprises a circuit 305 for leveling the control signal of the switch Si, for example a voltage and / or current amplifier (to be able to charge the grid in the case of a MOS switch), the input of which is connected to the output of the circuit 303 and the output of which is connected to a control node of the switch Si. The circuit 305 is adapted to transpose the logic control signal supplied by the circuit 303 as a level signal suitable for effectively controlling the switch.
    Figure 4 is a more detailed diagram of an embodiment of the circuit of Figure 3. The circuit of Figure 4 shows the same elements as the circuit of Figure 3, and illustrates in more detail an embodiment of the switch Si and of the circuit 301 for detecting the cancellation of the voltage at the terminals of the switch Si.
    In this example, we consider a switch Si equivalent to two MOS transistors Ml and M2 connected in anti-series by their sources (s). The drains (d) of the transistors Ml and M2 respectively form the two conduction nodes Kl and K2 of the switch Si. The gates (g) of the transistors Ml and M2 are connected in a node CMD forming the control node of the switch Si. The node REF common to the source (s) of the transistors Ml and M2 forms a reference node of the switch, to which the control signal applied to the node CMD is referenced.
    Circuit 301 includes a first resistive voltage divider bridge comprising a resistor rl in series with a resistor r2, providing an attenuated image of the drain voltage
    B15711 - DD17721SP source of transistor Ml, and a second resistive voltage divider bridge comprising a resistor rl 'in series with a resistor r2', providing an attenuated image of the drain-source voltage of transistor M2. In this example, the resistor rl has a first end connected to the node K1 and a second end connected to a node Q, and the resistor r2 has a first end connected to the node Q and a second end connected to the node REF. In addition, in this example, the resistor rl 'has a first end connected to the node K2 and a second end connected to a node R, and the resistor r2' has a first end connected to the node R and a second end connected to the node REF. By way of example, the resistors rl and rl 'are identical, and the resistors r2 and r2' are identical (apart from the manufacturing dispersions).
    The circuit 301 further comprises a voltage comparator 421 referenced to the node REF. The output node Q of the first voltage divider bridge (rl, r2) is connected to the positive input (+) of comparator 421, and the output node R of the second voltage divider bridge (rl ', r2') is connected to the negative (-) input of comparator 421.
    The output of comparator 421 forms the output of circuit 301, connected to the input of circuit 303 (also referenced to the REF node). As described previously in relation to FIG. 3, the output of circuit 303 is connected to the input of the amplification stage 305, the output of the amplification stage 305 being connected to the node CMD for controlling the switch Si.
    It will be noted that in the example of FIG. 4, the entire control chain of the switch Si, from the detection of the zero crossing of the voltage across the terminals of the switch until the effective control of the switch, is referenced to the same potential, namely the potential of the reference node REF of the switch. Thus, the control circuit of FIG. 4 does not include an insulation element which allows great reactivity of the circuit. In particular, this makes it possible to order without significant delay the closing of the switch Si during
    B15711 - DD17721SP the cancellation of the voltage across its terminals, and therefore to keep the switching losses in the switch at a very low level.
    It will be noted that in the embodiment of FIG. 1, the capacitors C1, C2, C3, C4 make it possible to slow down the voltage variations at the terminals of the switches SI, S2, S3, S4 of the primary bridge H1 during the switching operations, so to facilitate detection of the zero crossing of the voltage across their terminals. Alternatively, these capacitors can be omitted.
    Second embodiment - inductive structure
    FIG. 5 is an electrical diagram of an example of an AC-DC converter 500 according to a second embodiment.
    The converter 500 comprises a first H-controlled bridge H1, or primary bridge, followed by an isolation transformer T comprising a primary winding W1 and a secondary winding W2 magnetically coupled, followed by a second H-controlled bridge H2, or secondary bridge.
    The bridge H1 consists of four switches controlled bidirectionally in current and voltage SI, S2, S3 and S4, for example identical (apart from manufacturing dispersions), each comprising two main conduction nodes and at least one control node. The switches SI and S4 are connected in series, by their conduction nodes, between input nodes C and D of the bridge. The switches S2 and S3 are connected in series, by their conduction nodes, between the nodes C and D, in parallel with the branch comprising the switches SI and S4. The midpoint E between the switches SI and S4 defines a first output node of the bridge, and the midpoint F between the switches S2 and S3 defines a second output node of the bridge. More particularly, in the example shown, the switch SI has a first conduction node connected to the node C and a second conduction node connected to the node E, the switch S4 has a first conduction node connected to the
    B15711 - DD17721SP node E and a second conduction node connected to node D, switch S2 has a first conduction node connected to node C and a second conduction node connected to node F, and switch S3 has a first node conduction connected to node F and a second conduction node connected to node D.
    The input nodes C and D of the bridge H1 are connected directly, that is to say without intermediate diode rectification stage or low-pass filtering stage, to nodes A and B of application of the converter input AC voltage.
    The output nodes E and F of the bridge H1 are connected to the ends G and H of the primary winding W1 of the transformer T.
    According to one aspect of the second embodiment, the primary bridge H1 is purely inductive at the input and at the output. More particularly, the converter 500 comprises an inductance LI connected in series with the bridge, via the input nodes C and D of the bridge, between the nodes A and B of application of the alternating input voltage of the converter, and a inductance LO connected in series with the bridge, via the output nodes E and F of the bridge, between the ends G and H of the primary winding W1 of the transformer T. In the example shown, the inductance LI has a first end connected to node C and a second end connected to node A, and node D is connected to node B. In addition, in this example, the inductor LO has a first end connected to node E and a second end connected to node G , and the node F is connected to the node H. In the embodiment of FIG. 5, the converter does not include a capacitive element connected at the input of the bridge Hl, between the nodes C and D, and also does not include of capacitive element con connected at the exit of the bridge Hl, between the nodes E and F. It will be noted that this is again an unusual arrangement. In fact, in power electronics, passive elements of electrical energy exchange of different natures are generally provided for.
    B15711 - DD17721SP entry and exit of the same H-shaped bridge, for reasons of compliance with the source association rules.
    The bridge H2 consists of four controlled switches S5, S6, S7 and S8, for example identical (apart from manufacturing dispersions), each comprising two main conduction nodes and at least one control node. The switches S5, S6, S7 and S8 are for example quasi-bidirectional switches, that is to say adapted to allow current to flow in both directions, but only allowing current control in one direction (in other words bidirectional switches in current but unidirectional in voltage). As a variant, the switches S5, S6, S7, S8 are bidirectional current and voltage switches. The switches S5 and S8 are connected in series, by their conduction nodes, between input nodes K and L of the bridge. The switches S6 and S7 are connected in series, by their conduction nodes, between the nodes K and L, in parallel with the branch comprising the switches S5 and S8. The midpoint M between switches S5 and S8 defines a first output node of the bridge, and the midpoint N between switches S6 and S7 defines a second output node of the bridge. More particularly, in the example shown, the switch S5 has a first conduction node connected to the node L and a second conduction node connected to the node M, the switch S8 has a first conduction node connected to the node M and a second conduction node connected to node K, switch S6 has a first conduction node connected to node L and a second conduction node connected to node N, and the switch S7 has a first conduction node connected to node N and a second conduction node connected to node K.
    The input nodes K and L of the bridge H2 are connected respectively to the ends I and J of the secondary winding W2 of the transformer T. In the example shown, the end I of the winding W2 is connected to the node K and the end J of the winding W2 is connected to the node L.
    B15711 - DD17721SP
    The converter 500 further comprises an output filtering capacitor CF, at the output of the bridge H2. In the example shown, the electrodes of the capacitor CF are connected respectively to the nodes M and N of the output of the bridge H2.
    The output nodes M and N of the bridge H2 are connected respectively to nodes O and P for supplying the DC output voltage of the converter 500. In the example shown, the node M is connected to the node O and the node N is connected to node P.
    The converter 500 further comprises a circuit 501 (not detailed) for controlling the switches SI, S2, S3, S4, S5, S6, S7 and S8 of the bridges H1 and H2.
    In operation, a load L to be supplied, for example an electric battery, can be connected between the nodes O and P of the converter output.
    The operation of the converter 500 is as follows.
    The circuit 501 controls the primary bridge Hl alternately in a first configuration in which the switches SI and S3, defining a first diagonal of the bridge, are closed (passers-by) and the switches S2 and S4, defining a second diagonal of the bridge, are open ( blocked), and in a second configuration in which the switches SI and S3 are open and the switches S2 and S4 are closed. As in the first embodiment, the switching frequency of the bridge Hl between the first and second configurations, or switching frequency, is preferably chosen to be much higher than the frequency of the AC voltage to be converted, for example between 200 kHz and 20 MHz for an input frequency of the order of 20 to 100 Hz. The duty cycle φΗΙ of the switching between the first and second configurations of the bridge H1 is for example approximately equal to 0.5.
    The circuit 501 also controls the secondary bridge H2 alternately in a first configuration in which the switches S5 and S7, defining a first diagonal of the bridge, are closed and the switches S6 and S8, defining a
    B15711 - DD17721SP second diagonal of the bridge, are open, and in a second configuration in which the switches S5 and S7 are open and the switches S6 and S8 are closed. The switching frequency of the bridge H2 between the first and second configurations is substantially equal to the switching frequency of the bridge H1. The duty cycle φΗ2 of the switching between the first and second configurations of the bridge H2 can however be different from the duty cycle φΗΙ of the primary bridge. In addition, a phase shift ÔH1H2 can be provided between the control sequence of the primary bridge H1 and the control sequence of the secondary bridge H2.
    As in the first embodiment, by playing on the parameters φΗ2 and ÔH1H2, the circuit 501 regulates the DC output voltage of the converter 500, and / or the current drawn from the AC supply voltage source of the converter, for example to ensure a sinusoidal absorption of the current supplied by the alternative source.
    In addition, as in the first embodiment, the converter of FIG. 5 is reversible. Thus, in the case where an active load L, for example a battery, is connected at the output of the converter, the circuit 501 can, by playing on the parameters φΗΙ, φΗ2 and / or ÔH1H2, control a transfer of electrical energy DC -AC, from the continuous load L to the AC input of the converter.
    According to one aspect of the second control circuit mode 501 is configured for, transition between the first passing and diagonal configuration S2, S4 blocked) configuration (diagonal SI, S3 blocked and passing) of the primary bridge Hl, do not open the embodiments, during phases (diagonal SI, and the second one of
    S3 diagonal S2, S4 switches SI and
    S3 only when the current flowing through them is canceled, and, during the transition phases between the second configuration (diagonal SI, blocked S3 and diagonal S2, S4 passing) and the first configuration (diagonal SI, S3 passing and diagonal S2, S4
    B15711 - DD17721SP blocked) from bridge Hl, open switches S2 and S4 only when the current flowing through them is canceled.
    This makes it possible to significantly limit the switching losses in the primary bridge H1. The converter switching frequency can then be chosen relatively high, for example greater than 1 MHz or even greater than 10 MHz, which makes it possible to significantly reduce the dimensions of the isolation transformer T.
    In a preferred embodiment, the switches S1, S2, S3, S4 of the primary bridge H1 and the switches S5, S6, S7, S8 of the secondary bridge H2 are gallium nitride switches. However, the embodiments described are not limited to this particular example.
    FIG. 6 is a timing diagram illustrating the operation of the converter 500 of FIG. 5 during a transition phase from the first configuration (diagonal SI, S3 passing and diagonal S2, S4 blocked) to the second configuration (diagonal SI, S3 blocked and diagonal S2, S4 passing) of the primary bridge Hl.
    More particularly, the timing diagram of FIG. 6 comprises a first curve Ιρθ representing the evolution, as a function of time, of the current Ιρθ flowing in the output inductance LO of the primary bridge Hl, a second curve Ig] _ representing the evolution , as a function of time, of the current Ig] _ flowing in the switch S1, and a third curve Igg representing the evolution, as a function of time, of the current Igg flowing in the switch S2.
    In the example of FIG. 6, one places oneself at an initial instant t0 at which the primary bridge H1 is in the first configuration. The switches SI and S3 are then conducting and the switches S2 and S4 blocked, and the current Ιρθ flowing in the inductance LO is substantially equal to the current I e flowing in the input inductance LI of the bridge Hl at the instant considered . Taking into account that the converter switching frequency is much higher than the frequency of the alternating voltage
    B15711 - DD17721SP input of the converter, the alternating input current I e is considered constant throughout the duration of a transition phase between the first and second configurations of the bridge Hl. At time t0, the current Igj_ in the switch SI is substantially equal to the input current I e (switch SI on), and the current Igg in the switch S2 is substantially zero (switch S2 blocked). In addition, the current I53 (not shown) in the switch S3 is substantially equal to the input current I e , and the current I54 (not shown) in the switch S4 is substantially zero.
    At an instant tl posterior to the instant tO, marking the beginning of a transition phase between the first and second configurations of the primary bridge Hl, the circuit 501 commands the closing of the switch S2, while maintaining the switches SI and S3 closed and switch S4 open. The inductance LO then discharges until canceling the current flowing in the primary winding W1 of the transformer, and therefore the current Ig] _ flowing in the switch SI. At the same time, the current I52 increases until reaching the value I e .
    The SI switch is configured to open automatically when the current flowing through it is canceled. Thus, at an instant t2 posterior to the instant tl, the switch SI opens.
    At an instant t3 subsequent to the instant t2, the circuit 501 commands the closing of the switch S4, while keeping the switches S2 and S3 closed and the switch SI open. The inductance LO then charges negatively until the current flowing through it reaches the value -I e . At the same time, the current I54 passing through the switch S4 increases until reaching the value I e , and the current I53 passing through the switch S3 decreases until it is canceled.
    The switch S3 is configured to open automatically when the current flowing through it is canceled. Thus, at an instant t4 subsequent to the instant t3, the switch S3 opens.
    B15711 - DD17721SP
    The instant t4 marks the end of the transition phase between the first and second configurations of the primary bridge H1. The switches S2 and S4 are then conducting and the switches SI and S3 blocked.
    The operation of the converter 500 during the transition phases from the second configuration (diagonal SI, blocked S3 and diagonal S2, S4 passing) to the first configuration (diagonal SI, S3 passing and diagonal S2, S4 blocked) of the primary bridge H1 is similar to what has just been described, that is to say that the circuit 501 first controls the closing of the switch SI while keeping the switches S2 and S4 closed and the switch S3 open, then, after the automatic opening of the switch S2, the closing of the switch S3 while keeping the switches SI and S4 closed and the switch S2 open, until the automatic opening of the switch S4.
    Thus, in the operating example described in relation to FIG. 6, each of the switches Si of the primary bridge H1 must be able to be commanded to close by the control circuit 501, and must be adapted, after closing, to reopen automatically when the current flowing through it vanishes.
    FIGS. 7A and 7B schematically illustrate an exemplary embodiment of a switch Si of the primary bridge H1 adapted to the operating mode described in relation to FIG. 6.
    In this example, we consider a switch Si equivalent to two MOS transistors Ml and M2 connected in anti-series by their drains (d). The sources (s) of the transistors Ml and M2 respectively form the two conduction nodes Kl and K2 of the switch Si. The gate (g) of the transistor Ml is connected to a node CMD1 forming a first control node of the switch The gate (g) of the transistor M2 is connected to a node of CMD2 forming a second control node of the switch Si.
    B15711 - DD17721SP
    The control circuit 501 of the converter 500 is configured to, when it orders the closing of a switch Si of the primary bridge Hl, strike the switch so that it behaves like a diode, and therefore that it can s open naturally when the current between its conduction nodes K1 and K2 vanishes. For this, when the switch Si closes, the circuit 501 applies a closing control signal to the gate of one of the two transistors Ml and M2 and maintains a blocking signal on the gate of the other transistor. .
    More particularly, in the example shown, in the case where a negative current must flow between the conduction nodes Kl and K2 of the switch, a positive gate-source voltage is applied to the transistor Ml (voltage VI between the node CMD1 and the node K1), and a zero or negative gate-source voltage is applied to the transistor M2 (voltage V2 between the node CMD2 and the node K2). In this case, the switch Si behaves like a diode whose anode is connected to node K2 and whose cathode is connected to node K1. This configuration is illustrated in FIG. 7A.
    In the case where a positive current must flow between the conduction nodes Kl and K2 of the switch, a negative or zero gate-source voltage is applied to the transistor Ml (voltage VI between the node CMD1 and the node Kl), and a positive gate-source voltage is applied to transistor M2 (voltage V2 between node CMD2 and node K2). In this case, the switch Si behaves like a diode, the anode of which is connected to the node K1 and the cathode of which is connected to the node K2. This configuration is illustrated in Figure 7B.
    Particular embodiments have been described. Various variants and modifications will appear to those skilled in the art. In particular, the embodiments described are not limited to the examples of numerical values mentioned by way of example in the present description.
    B15711 - DD17721SP
    权利要求:
    Claims (9)
    [1" id="c-fr-0001]
    1. Circuit (500) for converting an alternating voltage into a direct voltage, comprising:
    first four bidirectional switches (SI, S2, S3, S4) forming a first bridge in H (Hl), first (C) and second (D) input nodes of the bridge (Hl) being connected respectively to first (A ) and second (B) nodes for applying the alternating voltage;
    a transformer (T) comprising a primary winding (Wl) and a secondary winding (W2) magnetically coupled, first (G) and second (H) ends of the primary winding (Wl) being connected respectively to first (E) and second (F) output nodes of the first bridge (Hl);
    a first inductor (LI) connected in series with the first bridge (Hl) between the first node (C) of the bridge input and the first node (A) of application of the AC voltage;
    a second inductor (LO) connected in series with the first bridge (Hl), between the first node (E) of the bridge output and the first end (G) of the primary winding (Wl); and a control circuit (501) adapted to control the first bridge (Hl) alternately in a first configuration in which the switches (SI, S3) of a first diagonal of the bridge are closed and the switches of a second diagonal (S2 , S4) of the bridge are open, and in a second configuration in which the switches (SI, S3) of the first diagonal are open and the switches (S2, S4) of the second diagonal are closed, the control circuit (501) being adapted, during a transition phase between the first and second configurations, to, successively:
    close a first switch (S2) of the second diagonal (S2, S4);
    open a first switch (SI) of the first diagonal (SI, S3) when the current passing through this switch is canceled;
    B15711 - DD17721SP
    to close the second light switch (S4) of the second diagonal (S2, S4 ); andto open the second light switch (S3) of the first diagonal (IF, S3 ) when the crossing current this light switch
    is canceled.
    [2" id="c-fr-0002]
    2. Conversion circuit (500) according to claim
    1, further comprising four second switches (S5, S6, S7, S8) forming a second bridge in H (H2), first (K) and second (L) input nodes of the second bridge (H2) being connected respectively at first (I) and second (J) ends of the secondary winding (W2) of the transformer (T), and first (M) and second (N) output nodes of the second bridge (H2) being connected respectively to first (O) and second (P) nodes for supplying the DC voltage.
    [3" id="c-fr-0003]
    3. Conversion circuit (500) according to claim
    2, in which the control circuit (501) is adapted to control the second bridge (H2) alternately in a first configuration in which the switches (S6, S8) of a first diagonal of the bridge are closed and the switches (S5, S7) of a second diagonal of the bridge are open, and in a second configuration in which the switches (S6, S8) of the first diagonal are open and the switches (S5, S7) of the second diagonal are closed.
    [4" id="c-fr-0004]
    4. Conversion circuit (500) according to claim
    3, in which the control circuit (501) is configured to switch the first bridge (Hl) between its first and second configurations and to switch the second bridge (H2) between its first and second configurations at substantially the same frequency.
    [5" id="c-fr-0005]
    5. Conversion circuit (500) according to any one of claims 1 to 4, in which the control circuit (501) is configured to switch the first bridge (Hl) between its first and second configurations at a frequency greater than or equal at 1 MHz.
    B15711 - DD17721SP
    [6" id="c-fr-0006]
    6. Conversion circuit (500) according to any one of claims 1 to 5, in which each first switch (Si) is adapted to be commanded to close by the control circuit (501) and to open automatically when the current flowing through it vanishes.
    [7" id="c-fr-0007]
    7. Conversion circuit (500) according to any one of claims 1 to 6, in which each first switch (Si) is equivalent to an anti-series association of first (Ml) and second (M2) MOS transistors connected by their drains, the sources of the first (Ml) and second (M2) transistors respectively forming the conduction nodes (Kl, K2) of the switch (Si), and the gates of the first (Ml) and second (M2) transistors
    MOS forming first (CMD1) and second (CMD2) switch control nodes.
    [8" id="c-fr-0008]
    8. Conversion circuit (500) according to claim
    7, in which the control circuit (501) is configured to, when it orders the closing of a switch (Si) of the first bridge (Hl), apply a closing control signal to the gate of one of the first (Ml) and second (M2) transistors of the switch and maintain a blocking signal on the gate of the other transistor.
    [9" id="c-fr-0009]
    9. Conversion circuit (500) according to claim
    8, in which the control circuit (501) is configured to, when it orders the closing of a switch (Si) of the first bridge (Hl), applying a closing control signal to the gate of the first transistor (Ml ) and a blocking signal on the gate of the second transistor (M2) when the current to be driven by the switch (Si) is of a first polarity, and apply a closing control signal to the gate of the second transistor (M2 ) and a blocking signal on the gate of the first transistor (Ml) when the current which the switch (Si) is to conduct is of a second polarity opposite to the first polarity.
    B15711 - DD17721SP 3410. Conversion circuit (500) according to any one
    claims 1 to 9, wherein the first switches (SI, S2, S3, S4) are gallium nitride switches.
    B 15711 DD17721SP
    1/4
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    US10425014B2|2019-09-24|
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    法律状态:
    2018-01-31| PLFP| Fee payment|Year of fee payment: 2 |
    2018-07-13| PLSC| Search report ready|Effective date: 20180713 |
    2020-01-30| PLFP| Fee payment|Year of fee payment: 4 |
    2021-10-08| ST| Notification of lapse|Effective date: 20210905 |
    优先权:
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    FR1750209A|FR3061817B1|2017-01-10|2017-01-10|AC-DC POWER CONVERTER|
    FR1750209|2017-01-10|FR1750209A| FR3061817B1|2017-01-10|2017-01-10|AC-DC POWER CONVERTER|
    EP18150659.3A| EP3346597B1|2017-01-10|2018-01-08|Ac-dc power converter|
    US15/866,403| US10425014B2|2017-01-10|2018-01-09|Bidirectional AC/DC H-bridge power converter|
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